Method and system for channel estimation processing for interference suppression

ABSTRACT

Aspects of a method and system for channel estimation for interference suppression are provided. In this regard, one or more circuits and/or processors of a mobile communication device may generate and/or receive a first set of channel estimates and a second set of channel estimates. The one or more circuits and/or processors may modify the second set of channel estimates based on a comparison of a measure of correlation between the first set of channel estimates and the second set of channel estimates with a threshold. The first set of channel estimates and/or the modified second set of channel estimates may be utilized for cancelling interference in received signals. The first set of channel estimates may be associated with a first transmit antenna of a base transceiver station and the second set of channel estimates may be associated with a second transmit antenna of the base transceiver station.

CROSS-REFERENCE TO RELATED APPLICATIONS/INCORPORATION BY REFERENCE

This application makes reference to:

-   U.S. patent application Ser. No. 12/582,771 filed on Oct. 21, 2009;-   U.S. patent application Ser. No. 12/604,978 filed on Oct. 23, 2009;-   U.S. Patent Application Ser. No. 61/242,524 filed on Sep. 15, 2009;-   U.S. patent application Ser. No. 12/573,803 filed on Oct. 5, 2009;-   U.S. patent application Ser. No. 12/604,976 filed on Oct. 23, 2009;-   U.S. patent application Ser. No. 12/611,810 filed on Nov. 3, 2009;-   U.S. Patent Application Ser. No. 61/246,797 filed on Sep. 29, 2009;-   U.S. patent application Ser. No. 12/575,879 filed on Oct. 8, 2009;-   U.S. patent application Ser. No. 61/288,008 filed on Dec. 18, 2009;-   U.S. Patent Application Ser. No. 61/242,554 filed on Sep. 15, 2009;-   U.S. patent application Ser. No. 12/612,272 filed on Nov. 4, 2009;-   U.S. patent application Ser. No. 12/575,840 filed on Oct. 8, 2009;-   U.S. patent application Ser. No. 12/605,000 filed on Oct. 23, 2009;-   U.S. patent application Ser. No. 12/543,283 filed on Aug. 18, 2009;-   U.S. patent application Ser. No. 12/570,736 filed on Sep. 30, 2009;-   U.S. patent application Ser. No. 12/577,080 filed on Oct. 9, 2009;    and-   U.S. patent application Ser. No. 12/603,304 filed on Oct. 21, 2009.

Each of the above referenced applications is hereby incorporated hereinby reference in its entirety.

FIELD OF THE INVENTION

Certain embodiments of the invention relate to signal processing. Morespecifically, certain embodiments of the invention relate to a methodand system for channel estimation for interference suppression.

BACKGROUND OF THE INVENTION

Wideband code division multiple access (WCDMA) is a third generation(3G) cellular technology that enables the concurrent transmission of aplurality of distinct digital signals via a common RF channel. WCDMAsupports a range of communications services that include voice, highspeed data and video communications. One such high speed datacommunications service, which is based on WCDMA technology, is the highspeed downlink packet access (HSDPA) service.

WCDMA is a spread spectrum technology in which each digital signal iscoded or “spread” across the RF channel bandwidth using a spreadingcode. Each of the bits in the coded digital signal is referred to as a“chip”. A given base transceiver station (BTS), which concurrentlytransmits a plurality of distinct digital signals, may encode each of aplurality of distinct digital signals by utilizing a different spreadingcode for each distinct digital signal. At a typical BTS, each of thesespreading codes is referred to as a Walsh code. The Walsh coded digitalsignal may in turn be scrambled by utilizing a pseudo normal (PN) bitsequence to generate chips. An example of a PN bit sequence is a Goldcode. Each of a plurality of BTS within an RF coverage area may utilizea distinct PN bit sequence. Consequently, Walsh codes may be utilized todistinguish distinct digital signals concurrently transmitted from agiven BTS via a common RF channel while PN bit sequences may be utilizedto distinguish digital signals transmitted by distinct BTSs. Theutilization of Walsh codes and PN sequences may increase RF frequencyspectrum utilization by allowing a larger number of wirelesscommunications to occur concurrently within a given RF frequencyspectrum. Accordingly, a greater number of users may utilize mobilecommunication devices, such as mobile telephones, Smart phones and/orwireless computing devices, to communicate concurrently via wirelesscommunication networks.

A user utilizing a mobile communication device, MU_1, may be engaged ina communication session with a user utilizing a mobile communicationdevice MU_2 via a base transceiver station, BTS_A within wirelesscommunication network. For example, the mobile communication device MU_1may transmit a digital signal to the BTS_A, which the base transceiverstation BTS_A may then transmit to the mobile communication device MU_2.The base transceiver station BTS_A may encode signals received from themobile communication device MU_1 and transmitted to the mobilecommunication device MU_2 by utilizing a Walsh code, W_12, and a PNsequence, PN_A. The mobile communication device MU_2 may receive signalstransmitted concurrently by a plurality of base transceiver stations(BTSs) in addition to the base transceiver station BTS_A within a givenRF coverage area. The mobile communication device MU_2 may process thereceived signals by utilizing a descrambling code that is based on thePN sequence PN_A and a despreading code that is based on the Walsh codeW_12. In doing so, the mobile communication device MU_2 may detect ahighest relative signal energy level for signals received from basetransceiver station BTS_A, which comprise a digital signal correspondingto mobile communication device MU_1.

However, the mobile communication device MU_2 may also detect signalenergy from the digital signals, which correspond to signals from mobilecommunication devices other than the mobile communication device MU_1.The other signal energy levels from each of these other mobilecommunication devices may be approximated by Gaussian white noise, butthe aggregate noise signal energy level among the other mobilecommunication device may increase in proportion to the number of othermobile communication devices whose signals are received at the mobilecommunication device MU_2. This aggregate noise signal energy level maybe referred to as multiple access interference (MAI). The MAI may resultfrom signals transmitted by the base transceiver station BTS_A, whichoriginate from signal received at the base transceiver station BTS_Afrom mobile communication devices other than mobile communication deviceMU_1. The MAI may also result from signals transmitted by the basetransceiver stations BTSs other than the base transceiver station BTS_A.The MAI and other sources of noise signal energy may interfere with theability of MU_2 to successfully decode signals received from MU_1.

An additional source of noise signal energy may result from multipathinterference. The digital signal energy corresponding to the mobilecommunication device MU_2, which is transmitted by the base transceiverstation BTS_A may disperse in a wavefront referred to as a multipath.Each of the components of the multipath may be referred to as amultipath signal. Each of the multipath signals may experience adifferent signal propagation path from the base transceiver stationBTS_A to the mobile communication device MU_2. Accordingly, differentmultipath signals may arrive at different time instants at the mobilecommunication device MU_2. The time duration, which begins at the timeinstant that the first multipath signal arrives at the mobilecommunication device MU_2 and ends at the time instant that the lastmultipath signal arrives at the mobile communication device MU_2 isreferred to as a delay spread. The mobile communication device MU_2 mayutilize a rake receiver that allows the mobile communication device MU_2to receive signal energy from a plurality of multipath signals receivedwithin a receive window time duration. The receive window time durationmay comprise at least a portion of the delay spread time duration.Multipath signals, which are not received within the receive window timeduration may also contribute to noise signal energy.

Further limitations and disadvantages of conventional and traditionalapproaches will become apparent to one of skill in the art, throughcomparison of such systems with some aspects of the present invention asset forth in the remainder of the present application with reference tothe drawings.

BRIEF SUMMARY OF THE INVENTION

A method and system for channel estimation processing for interferencesuppression, substantially as illustrated by and/or described inconnection with at least one of the figures, as set forth morecompletely in the claims.

These and other advantages, aspects and novel features of the presentinvention, as well as details of an illustrated embodiment thereof, willbe more fully understood from the following description and drawings.

BRIEF DESCRIPTION OF SEVERAL VIEWS OF THE DRAWINGS

FIG. 1A is a diagram illustrating an exemplary wireless communicationsystem, which is operable to provide interference suppression in WCDMA,in accordance with an embodiment.

FIG. 1B is a diagram illustrating an exemplary wireless communicationsystem, which is operable to utilize transmit diversity and provideinterference suppression in WCDMA, in accordance with an embodiment.

FIG. 2 is a diagram of an exemplary communication device, which isoperable to provide interference suppression for WCDMA, in accordancewith an embodiment of the invention.

FIG. 3 is a diagram of an exemplary WCDMA receiver with interferencesuppression, in accordance with an embodiment of the invention.

FIG. 4 is a module diagram illustrating an exemplary interferencecancellation module, in accordance with an embodiment of the invention.

FIG. 5 is a diagram illustrating generation of normalized channelestimates, in accordance with an embodiment of the invention.

FIG. 6A is a is a diagram that illustrates exemplary orthogonalizationof channel estimates received from a transmit diversity antenna, inaccordance with an embodiment of the invention.

FIGS. 6B and 6C are diagrams that illustrate exemplary implementation ofan orthogonalization module, in accordance with an embodiment of theinvention.

FIG. 7 is a diagram that illustrates an exemplary implementation of anormalization module, in accordance with an embodiment of the invention.

FIG. 8 is a flowchart illustrating exemplary steps for interferencecancellation in a communication system that utilizes transmit diversity,in accordance with an embodiment of the invention.

DETAILED DESCRIPTION OF THE INVENTION

Certain embodiments of the invention may be found in a method and systemfor channel estimation for interference suppression. In variousembodiments of the invention, one or more circuits and/or processors ofa mobile communication device may generate and/or receive a first set ofchannel estimates and a second set of channel estimates. The first setof channel estimates may be associated with a plurality of RF channelsbetween a first transmit antenna of a base transceiver station and oneor more receive antennas of the mobile communication device. The basetransceiver station may be a non-listened base transceiver station. Thesecond set of channel estimates may be associated with a plurality of RFchannels between a second transmit antenna of the base transceiverstation and one or more receive antennas of the mobile communicationdevice. The one or more circuits and/or processors may modify the secondset of channel estimates based on a comparison of a measure ofcorrelation between the first set of channel estimates and the secondset of channel estimates with a threshold. The threshold may bedynamically or statically determined. The first set of channel estimatesand/or the modified second set of channel estimates may be utilized forprocessing received signals. In instances that the measure ofcorrelation is below the threshold, the second set of channel estimatesmay be modified such that the modified second set of channel estimatesis orthogonal to the first set of channel estimates. In instances thatthe measure of correlation is above the threshold, the second set ofchannel estimates may be modified by setting each of the channelestimates in the second set to zero.

The first set of channel estimates may be normalized with respect tototal power received over all of the plurality of RF channels betweenthe first transmit antenna and the one or more receive antennas. Thesecond set of channel estimates may be normalized with respect to totalpower received over all of the plurality of RF channels between thesecond transmit antenna and the one or more receive antennas. The secondset of channel estimates may be disregarded in instances that themeasure of correlation is above a threshold. Each channel estimate inthe first set of channel estimates may indicate a vector of complexchannel gains between the first transmit antenna and one of the one ormore receive antennas. Each channel estimate in the second set ofchannel estimates may indicates a complex channel gain between thesecond transmit antenna and one of the one or more receive antennas.Interference may be suppressed in the received signals based on thefirst set of channel estimates and/or the modified second set of channelestimates.

FIG. 1A is an illustration of an exemplary wireless communicationsystem, in accordance with an embodiment. Referring to FIG. 1A, there isshown a cell 100 and a BTS C 106. The cell 100 comprises BTS A 102, BTSB 104, mobile communication device MU_1 112 and mobile communicationdevice MU_2 114. The BTS 106 may be located outside of the cell 100.

The mobile communication devices MU_1 112 and MU_2 114 may be engaged ina communication via the BTS A 102. The mobile communication device MU_1112 may transmit signals to the BTS A 102 via an uplink RF channel 122.In response, the BTS A 102 may transmit signals to the mobilecommunication device MU_2 114 via a downlink RF channel 124. Signalstransmitted by the BTS A 102 may communicate chips that are generatedutilizing a scrambling code PN_A. The signals transmitted via RF channel124 may be spread utilizing a spreading code WC_12. The spreading codeWC_12 may comprise an orthogonal variable spreading factor (OVSF) code,for example a Walsh code, which enables the mobile communication deviceMU_2 114 to distinguish signals transmitted by the BTS A 102 via thedownlink RF channel 124 from signals transmitted concurrently by the BTSA 102 via other downlink RF channels, for example downlink RF channel126. The BTS A 102 may utilize one or more OVSF codes, WC_other, whenspreading data transmitted via downlink RF channel 126. The one or moreOVSF codes, WC_other, may be distinct from the OVSF code WC_12.

The mobile communication device MU_2 114 may receive MAI signals from RFchannel 126, RF channel 128 and/or RF channel 130. As stated above, thesignals received via RF channel 126 may be transmitted by the BTS A 102.The signals received via RF channel 128 may be transmitted by the BTS B104. The signals transmitted by the BTS 104 may be scrambled based on ascrambling code PN_B. The signals received via RF channel 130 may betransmitted by the BTS C 106. The signals transmitted by the BTS C 106may be scrambled based on a scrambling code PN_C.

The mobile communication device MU_2 114 may be operable to perform asoft handoff from the current serving BTS A 102 to any of a plurality ofBTSs located within the cell 100, for example, the BTS B 104.Accordingly, the mobile communication device MU_2 114 may be operable toprocess received signals based on scrambling code PN_A and/or scramblingcode PN_B. In this regard, the mobile communication device MU_2 114 maysend data to the BTS A 102 and/or the BTS B 104, and data destined formobile communication device MU_2 114 may be received via the BTS A 102and/or the BTS B 104. Thus, the BTS A 102 and the BTS B 104 may bereferred to as “listened” BTSs. Conversely, the mobile communicationdevice MU_2 114 may not be operable to perform a soft handoff from thecurrent serving BTS A 102 to a BTS that is outside of the cell 100—theBTS C 106, for example. In this regard, the mobile communication deviceMU_2 114 may not transmit data to the BTS C 106 or receive data destinedfor the mobile communication device MU_2 114 from the BTS C 106.Accordingly, the BTS A 102 and the BTS B 104 may be referred to as“non-listened” BTSs.

While the desired signal at the mobile communication device MU_2 114 maybe received via RF channel 124, the mobile communication device MU_2 114may also receive signal energy via the RF channel 126, the RF channel128 and/or the RF channel 130. The received signal energies from the RFchannels 126, 128 and/or 130 may result in MAI, which may interfere withthe ability of the mobile communication device MU_2 114 to receivedesired signals via RF channel 124. Accordingly, in various aspects ofthe invention, the mobile communication device MU_2 114 is operable tosuppress interference resulting from undesired signals transmitted bylistened BTSs. Additionally, even though the BTS is not a listened BTS,information transmitted on the RF channel 130—data transmitted to mobilecommunication devices other than mobile communication device MU_2114—may nevertheless interfere with the desired signals on the RFchannel 124. Accordingly, in various aspects of the invention, themobile communication device MU_2 114 is operable to suppressinterference from the non-listened BTS 106, or non-listened BTSs.

In various embodiments of the invention, the mobile communication deviceMU_2 may comprise suitable logic, circuitry and/or code that areoperable to receive signal energy via the RF channels 124, 126, 128and/or 130, and suppress interference signal energy received via the RFchannels 126, 128 and/or 130. The mobile communication device MU_2 mayutilize an iterative method for interference cancellation. The iterativemethod may comprise a weighting iteration, one or more weighting andaddback iterations, and an addback iteration. For the mobilecommunication devices 112 and 114 to process multipath information, eachof the channels 124, 126, 128, and 130 of FIG. 1A may represent multiplepaths, where those multiple paths are separated by a time delay.

FIG. 1B is a diagram illustrating an exemplary wireless communicationsystem, which is operable to utilize transmit diversity and provideinterference suppression in WCDMA, in accordance with an embodiment. InFIG. 1B, the BTS 102 is operable transmit a datastream via antennas 152Aand 152D. The datastream may be scrambled utilizing scrambling codePN_A, and spread utilizing spreading code WC_12, before beingtransmitted via antenna 152A onto RF channel 124. Additionally, thedatastream may be scrambled utilizing scrambling code PN_D, and spreadutilizing spreading code WC_12, before being transmitted via antenna152D and RF channel 156. The mobile communication device 114 may beoperable to receive and process both channels 156 and 124 such thatsignal reception is improved over the case in which only a singlechannel 124 is present. Accordingly, aspects of the invention may enableestimating energy present on the channels 156 and 124 and utilizing thechannel estimates to cancel or suppress interference received on thechannels 156 and 124. For the mobile communication devices 112 and 114operable to process multipath information, each of the channels 124,128, 130 and 156 of FIG. 1B may represent multiple paths, where thosemultiple paths are separated by a time delay

FIG. 2 is a diagram of an exemplary communication device, which mayutilize interference suppression for WCDMA, in accordance with anembodiment of the invention. Referring to FIG. 2, there is shown atransceiver system 200, a receiving antenna 222 and a transmittingantenna 232. The transceiver system 200 may comprise at least a receiver202, a transmitter 204, a processor 206, an interference cancellationmodule 210 and a memory 208. Although a separate receiver 202 andtransmitter 204 are illustrated by FIG. 2, the invention is not limited.In this regard, the transmit function and receive function may beintegrated into a single transceiver module. The transceiver system 200may also comprise a plurality of transmitting antennas and/or aplurality of receiving antennas, for example to support diversitytransmission and/or diversity reception. Various embodiments of theinvention may comprise a single antenna, which is coupled to thetransmitter 204 and receiver 202 via a transmit and receive (T/R)switch. The T/R switch may selectively couple the single antenna to thereceiver 202 or to the transmitter 204 under the control of theprocessor 206, for example.

The receiver 202 may comprise suitable logic, circuitry, interfacesand/or code that may be operable to perform receive functions that maycomprise PHY layer function for the reception or signals. These PHYlayer functions may comprise, but are not limited to, the amplificationof received RF signals, generation of frequency carrier signalscorresponding to selected RF channels, for example uplink or downlinkchannels, the down-conversion of the amplified RF signals by thegenerated frequency carrier signals, demodulation of data contained indata symbols based on application of a selected demodulation type, anddetection of data contained in the demodulated signals. The RF signalsmay be received via the receiving antenna 222. The receiver 202 may beoperable to process the received RF signals to generate basebandsignals. A chip-level baseband signal may comprise a plurality of chips.The chip-level baseband signal may be descrambled based on a PN sequenceand despread based on an OVSF code, for example a Walsh code, togenerate a symbol-level baseband signal. The symbol-level basebandsignal may comprise a plurality of data symbols. The receiver 202 maycomprise a rake receiver, which in turn comprises a plurality of rakefingers to process a corresponding plurality of received multipathsignals.

The transmitter 204 may comprise suitable logic, circuitry, interfacesand/or code that may be operable to perform transmit functions that maycomprise PHY layer function for the transmission or signals. These PHYlayer functions may comprise, but are not limited to, modulation ofreceived data to generate data symbols based on application of aselected modulation type, generation of frequency carrier signalscorresponding to selected RF channels, for example uplink or downlinkchannels, the up-conversion of the data symbols by the generatedfrequency carrier signals, and the generation and amplification of RFsignals. The RF signals may be transmitted via the transmitting antenna232.

The memory 208 may comprise suitable logic, circuitry, interfaces and/orcode that may enable storage and/or retrieval of data and/or code. Thememory 208 may utilize any of a plurality of storage mediumtechnologies, such as volatile memory, for example random access memory(RAM), and/or non-volatile memory, for example electrically erasableprogrammable read only memory (EEPROM).

The interference cancellation module 210 may comprise suitable logic,circuitry and/or code that are operable to suppress interferencesignals, relative to a desired signal, in a received signal. Thereceived signal may comprise one or more desired signals and one or moreinterference signals. The interference cancellation module 210 maygenerate interference suppressed versions of the one or more signals byreducing the signal level for the interference signals relative to thesignal level for the desired signals. In an exemplary embodiment of theinvention that utilizes transmit diversity, a pair of signals from apair of transmit antennas may be received via one or more channels bythe antenna 222 and processed by system 200. In the case of Txdiversity, the same scrambling code may be used on multiple transmitantennas. The interference cancellation module may treat each transmitantenna as an independent interferer, estimate each interfering signals,and subtract the interfering signals from the received signal that is acomposition of signals from multiple sources including the multipletransmit antennas. This may lead to a single interference beingsubtracted multiple times and therefore amplifying the detrimentaleffects of the interference. In order to avoid this, the channelestimation from each antenna is preprocessed such that the resultingchannel estimation representations have little mutual-correlation.

In operation, the receiver 202 may receive signals via the receivingantenna 222. In an exemplary embodiment of the invention, the receiver202 may comprise a rake receiver. The receiver 202 may communicatesignals to the processor 206 and/or to the interference cancellationmodule 210.

The receiver 202 may generate timing information that corresponds toeach of the fingers in the rake receiver portion of the receiver 202.Each of the fingers in the rake receiver may process signals that arereceived from a particular BTS within a delay spread time duration.Based on the received RF signals, the receiver may generate chip-levelbaseband signals. The receiver 202 may communicate the chip-levelbaseband signals to the interference cancellation module 210. The rakereceiver 202 may generate one or more symbol-level baseband signalsbased on a selected one or more OVSF codes and a selected one or more PNsequences. The symbol-level baseband signals may be communicated to theprocessor 206. The OVSF codes may be selected based on a specifieddesired user signal. For example, referring to FIG. 1B, the rakereceiver 202 associated with mobile communication device MU_2 may selectan OVSF code, WC_12, and PN sequences PN_A and PN_D, which may beutilized to generate the symbol-level baseband signal from thechip-level baseband signal.

The processor 206 may utilize common pilot channel (CPICH) information,communicated by the signals received from the receiver 202, to compute aplurality of channel estimate values or, in various embodiments of theinvention, the receiver 202 may compute the channel estimate values. Theprocessor 206 and/or receiver 202 may compute one or more channelestimate values corresponding to multipath signals transmitted by one ormore BTSs and received at a finger in the rake receiver. The computedchannel estimate values may be represented as a channel estimate matrix,w″_(b,t,r,f), where ‘b’ represents a numerical index that is associatedwith a given BTS, ‘t’ represents a numerical index that is associatedwith a given transmit antenna of the BTS ‘b’, ‘r’ represents a numericalindex that is associated with a given receive antenna of the system 200,and f represents a numerical index of the rake fingers associated withthe transmit antenna ‘t’ of the BTS ‘b’. The processor 206 may beoperable to communicate the computed channel estimate values to thereceiver 202 and to the interference cancellation module 210 and/or tothe memory 208. The processor 206 may compute and/or select one or moreinterference cancellation parameter values, which control the signalinterference cancellation performance of the interference cancellationmodule 210. The processor 206 may also be operable to communicate theinterference cancellation parameter values to the interferencecancellation module 210 and/or to the memory 208.

The processor 206 may also determine which BTSs are associated with acurrent cell 100 and which BTSs are not associated with the current cell100. For example, the processor 206 may determine that the BTS A 102 andthe BTS B 104 are associated with the current cell 100, while the BTS C106 is not associated with the current cell 100. In an exemplaryembodiment of the invention, the processor 206 may store one or more PNsequences for at least a portion of the BTSs that are associated withthe current cell 100. For example, referring to FIG. 1B, the processor206 may generate and/or store corresponding PN sequences, for examplePN_A, PN_D, and PN_B, in the memory 208. The PN sequences may begenerated on the fly based on the code structure utilized by the BTSand/or based on timing information associated with the BTS. The PNsequences PN_A, PN_D and PN_B may be associated with the current cell100.

In other exemplary embodiments of the invention, the processor 206 maystore PN sequences for at least a portion of the BTSs that areassociated with the current cell 100 and at least a portion of the BTSsthat are not associated with the current cell 100. For example,referring to FIG. 1B, the processor 206 may generate and/or storecorresponding PN sequences, for example PN_A, PN_B PN_C, and PN_D in thememory 208. In general, the processor 206 may store the PN sequences forthe BTSs from which a mobile communication device, for example themobile communication device MC_2 114, may expect to receive signals andthe processor 206 may store PN sequences from which the mobilecommunicating device may not expect to receive signals. The mobilecommunication device may expect to receive signals, for example commonpilot channel (CPICH) signals, from a plurality of BTSs in anticipationof a soft handoff from a current service BTS to a subsequent servingBTS.

The interference cancellation module 210 may receive signals from thereceiver 202, which correspond to received multipath signals. Thesignals received by the interference cancellation module 210 maycomprise chip-level baseband signals. A plurality of chips, for example256 chips, may be associated with a data symbol. The interferencecancellation module 210 may be operable to determine a time durationthat corresponds to a data symbol processing period. The interferencecancellation module 210 may be operable to determine whether to performiterations of a signal interference suppression on received chip-levelbaseband signals and/or symbol-level baseband signals, in accordancewith an embodiment of the invention, during each data symbol processingperiod.

The interference cancellation module 210 may retrieve a plurality ofchannel estimate values, one or more PN sequences, a plurality of OVSFcodes, and one or more interference cancellation parameter values frommemory 208. The interference cancellation module 210 may receive timinginformation from the receiver 202 that corresponds to each of thefingers in the rake receiver portion of the receiver 202.

The interference cancellation module 210 may process received signals,utilizing received timing information and channel estimate values, tocombine the multipath signals which are associated with correspondingfingers in the rake receiver. In various embodiments of the invention,the interface cancellation module 210 may combine the multipath signalsto generate a combined chip-level signal by utilizing, for example,maximal ratio combining (MRC) and/or equal gain combining (EGC). Theinterference cancellation module 210 may process the combined chip-levelsignal, by utilizing PN sequences and OVSF codes, to determine a signallevel associated with each of the plurality of OVSF codes for each ofone or more selected PN sequences. In an exemplary embodiment of theinvention, the plurality of OVSF codes comprises 256 Walsh codes. Eachsignal associated with an OVSF code may be referred herein as acorresponding user signal, although it should be noted that multipleOVSF codes may be associated with a single user and thus there is notnecessarily a one-to-one correspondence between OVSF codes and users.For example, a signal associated with a j^(th) OVSF code may be referredto as a j^(th) user signal. Referring to FIG. 1, for example, the OSVFcode WC_12 may be associated with a user signal that is transmitted fromBTS A 102 to the mobile telephone MC_2 114.

The interference cancellation module 210 may compute a signal powerlevel value and a noise power level value corresponding to each of theuser signals. Based on the computed signal power level value, noisepower level value, and the one or more interference cancellationparameter values, the interference cancellation module 210 may compute aweighting factor value corresponding to each user signal. The pluralityof weighting factor values associated with each BTS may be representedas a weighting factor matrix, A_(bts), where bts represents a numericalindex value that is associated with a given BTS. In an exemplaryembodiment of the invention, the weighting factor values for a given BTSmay be computed as illustrated by the following equations:

$\begin{matrix}{z_{j} \cong \frac{\lambda\; x_{j}^{2}}{{\lambda\; x_{j}^{2}} + y_{j}^{2}}} & \lbrack {1a} \rbrack \\{when} & \; \\{x_{j}^{2} > {\gamma\; y_{j}^{2}}} & \lbrack {1b} \rbrack \\{{and}\text{:}} & \; \\{z_{j} = 0} & \lbrack {1c} \rbrack \\{when} & \; \\{x_{j}^{2} < {\gamma\; y_{j}^{2}}} & \lbrack {1d} \rbrack\end{matrix}$where z_(j) represents the weighting factor value for the j^(th) usersignal and j may be, for example, an integer from 0 to J; x_(j) ²represents the signal power level value for the j^(th) user signal,which was generated by descrambling a received signal based on a PNsequence for the given BTS and despreading the descrambled signalutilizing the OVSF code associated with the j^(th) user; y_(j) ²represents the noise power level value for the j^(th) user signal, whichwas generated by descrambling the received signal based on the PNsequence for the given BTS and despreading the descrambled signalutilizing the OVSF code associated with the j^(th) user; and λ and γrepresent interference cancellation parameter values.

The weighting factor values z_(j) may correspond to a signal to noiseratio (SNR) measure for the j^(th) user signal. Values for z_(j) may bewithin the range 0≦z_(j) ²≦1. In one regard, values of z_(j) may be an apriori measure of confidence that a given user signal comprises validsignal energy that was transmitted by the BTS.

The interference cancellation module 210 may be operable to processchip-level signals received from one or more transmit antennas of one ormore BTSs to generate corresponding interference suppressed chip-levelsignals based on an iterative method for interference cancellation, inaccordance with an embodiment of the invention. The interferencesuppressed chip-level signals may be output to each corresponding rakefinger. Each of the rake fingers may then process its respectiveinterference suppressed chip-level signals.

The weighting factor value z(j) is a function of the interferencecancellation parameter values λ and γ. In various embodiments of theinvention, the interference cancellation parameters λ and γ may compriseinteger and/or non-integer values. In an exemplary embodiment of theinvention, λ=1 and γ=1. The processor 206 may be operable to monitor theinterference cancellation performance of the interference cancellationmodule 210, for example by measuring SNR values for processed signalsgenerated by the receiver 202 based on interference suppressedchip-level signals. Accordingly, the processor 206 may be operable toadjust one or both interference cancellation parameter values λ and γ.

FIG. 3 is a diagram of an exemplary WCDMA receiver with interferencesuppression, in accordance with an embodiment of the invention.Referring to FIG. 3, there is shown a WCDMA receiver 300 which may besubstantially similar to the receiver 200. The receiver 300 may comprisean interference cancellation module 302, a delay buffer 304, a HSDPAprocessor 306, an HSDPA switching device 308, interference cancellation(IC) bypass switching device 310, and a plurality of rake fingers 312₁-312 _(F). The interference cancellation module 302 may correspond tothe interference cancellation module 210 as presented in FIG. 2. Therake fingers 312 ₁-312 _(F) represent fingers in a rake receiver. In anexemplary embodiment of the invention, the HSDPA switching device 308and the IC bypass switching device 310 may be configured by theprocessor 206.

The delay buffer 304 may comprise suitable logic, circuitry, interfacesand/or code that may be operable to receive a burst of a chip-levelsignal 324 as input at a given input time instant and output it as aburst of a chip-level signal 326 at a subsequent output time instant.The time duration between the input time instant and the output timeinstant may be referred to as a delay time duration. In an exemplaryembodiment of the invention, the delay time duration corresponds to 512chips.

The HSDPA processor 306 may comprise suitable logic, circuitry,interfaces and/or code that may be operable to provide HSDPA processingof received signals.

In operation, the HSDPA switching device 308 may comprise suitablelogic, circuitry, interfaces and/or code that are operable to select aninput signal to the HSDPA processor 306. As illustrated with respect toFIG. 3, the HSDPA switching device 308 is configured so that it isoperable to supply an interference suppressed signal 328, generated bythe interference cancellation module 302, as an input to the HSDPAprocessor 306. As indicated in FIG. 3, this configuration of the HSDPAswitching device 308 may result in the HSDPA switching device 308operating in a HSDPA interference cancellation (IC) mode.

The HSDPA switching device 308 may also be configured so that it isoperable to supply the baseband signal 324, generated by the receiver202, as an input to the HSDPA processor 306. As indicated in FIG. 3,this configuration of the HSDPA switching device 308 may result in theHSDPA switching device 308 operating in a normal HSDPA mode.

The HSDPA switching device 308 may also be configured such that no inputsignal is supplied to the HSDPA processor 306. As indicated in FIG. 3,this configuration of the HSDPA switching device 308 may result in theHSDPA switching device 308 operating in a HSDPA data path off mode.

The IC bypass switching device 310 may comprise suitable logic,circuitry, interfaces and/or code that are operable to select an inputsignal to the rake fingers 312 ₁-312 _(F). As illustrated by FIG. 3, theIC bypass switching device 310 is configured so that it is operable tosupply an interference suppressed signal 322, generated by theinterference cancellation module 302, as an input to the rake fingers312 ₁-312 _(F).

The IC bypass switching device 310 may also be configured so that it isoperable to supply a signal 326, which is output from the delay buffer304, as an input to the rake fingers 312 ₁-312 _(F). The signal 326output from the delay buffer 304 may comprise a time-delayed, andpossibly up-sampled or down-sampled, version of the signal 324 generatedby the receiver 202. As indicated in FIG. 3, the signal 326 output fromthe delay buffer 304 may comprise unsuppressed interference.

Each of the rake fingers 312 ₁-312 _(F) may receive, as input, thechip-level baseband signal 324 generated by the receiver 202. Based onthe input baseband signal 324 from the receiver 202, each of the rakefingers 312 ₁-312 _(F) may generate one or more channel estimates andrake finger timing information. In various embodiments of the invention,each rake finger 312 ₁-312 _(F) may generate the channel estimatesand/or rake finger timing information for selected multipath signalsbased on CPICH data received via the input baseband signal 324 receivedfrom the receiver 202. In the case of a single receive antenna, eachfinger 312 _(f) may be allocated and/or associated with one or moretransmit antennas of a particular BTS and may generate channel estimatesw″_(b,t)(f), for 1≦t≦T(b), where T(b) represents the number of transmitantennas of the BTS ‘b’. The channel estimate w″_(b,t)(f) may indicatethe complex channel gain between the antenna ‘t’ of BTS ‘b’ and thereceiver 300, for the finger ‘f’. In an exemplary embodiment of theinvention, the receiver 300 may comprise fingers 312 ₁-312 ₈, fingers312 ₁-312 ₄ may be allocated for processing signals from a firsttransmit-diversity BTS, and fingers 312 ₅-312 ₈ may be allocated forprocessing signals from a second transmit-diversity BTS. In such anembodiment of the invention, the generated channel estimates may be asdepicted in Table 1.

TABLE 1 Finger Generated Channel Estimates 312₁ w″_(1, 1)(1),w″_(1, 2)(1) 312₂ w″_(1, 1)(2), w″_(1, 2)(2) 312₃ w″_(1, 1)(3),w″_(1, 2)(3) 312₄ w″_(1, 1)(4), w″_(1, 2)(4) 312₅ w″_(2, 1)(1),w″_(2, 2)(1) 312₆ w″_(2, 1)(2), w″_(2, 2)(2) 312₇ w″_(3, 1)(1),w″_(3, 2)(1) 312₈ w″_(3, 1)(2), w″_(3, 2)(2)

In another exemplary embodiment of the invention, the receiver 300 maycomprise eight fingers; fingers 312 ₁-312 ₄ may be allocated forprocessing signals from transmit-diversity BTS b=1, fingers 312 ₅-312 ₆may be allocated for processing signals from non-diversity BTS b=2, andfingers 312 ₇-312 ₈ may be allocated for processing signals fromnon-transmit-diversity BTS b=3. The channel estimates w″_(b,t)(f) forsuch an exemplary embodiment are depicted in table 2.

TABLE 2 Finger Generated Channel Estimates 312₁ w″_(1, 1)(1),w″_(1, 2)(1) 312₂ w″_(1, 1)(2), w″_(1, 2)(2) 312₃ w″_(1, 1)(3),w″_(1, 2)(3) 312₄ w″_(1, 1)(4), w″_(1, 2)(4) 312₅ w″_(2, 1)(1) 312₆w″_(2, 1)(2) 312₇ w″_(3, 1)(1) 312₈ w″_(3, 1)(2)

In instances that the receiver comprises a plurality ‘R’ of receiveantennas, each rake finger 312 _(f) may generate channel estimatesw″_(b,t,1)(f) . . . w″_(b,t,R)(f), for 1≦t≦T(b) and 1≦r≦R. The channelestimate w″_(b,t,r)(f) may indicate the complex channel gain between theantenna ‘t’ of BTS ‘b’ and the receive antenna ‘r’ of the receiver 300,for the finger ‘f’. In an exemplary embodiment of the invention, thereceiver 300 may comprise two receive antennas and eight fingers,fingers 312 ₁-312 ₄ may be allocated for processing signals fromtransmit-diversity BTS b=1, fingers 312 ₅-312 ₈ may be allocated forprocessing signals from transmit-diversity BTS b=2. In such anembodiment, the channel estimates depicted in table 3 may be generated.

TABLE 3 Finger Generated Channel Estimates 312₁ w″_(1, 1, 1)(1),w″_(1, 2, 1)(1), w″_(1, 1, 2)(1), w″_(1, 2, 2)(1) 312₂ w″_(1, 1, 1)(2),w″_(1, 2, 1)(2), w″_(1, 1, 2)(2), w″_(1, 2, 2)(2) 312₃ w″_(1, 1, 1)(3),w″_(1, 2, 1)(3), w″_(1, 1, 2)(3), w″_(1, 2, 2)(3) 312₄ w″_(1, 1, 1)(4),w″_(1, 2, 1)(4), w″_(1, 1, 2)(4), w″_(1, 2, 2)(4) 312₅ w″_(2, 1, 1)(1),w″_(2, 2, 1)(1), w″_(2, 1, 2)(1), w″_(2, 2, 2)(1) 312₆ w″_(2, 1, 1)(2),w″_(2, 2, 1)(2), w″_(2, 1, 2)(2), w″_(2, 2, 2)(2) 312₇ w″_(2, 1, 1)(3),w″_(2, 2, 1)(3), w″_(2, 1, 2)(3), w″_(2, 2, 2)(3) 312₈ w″_(2, 1, 1)(4),w″_(2, 2, 1)(4), w″_(2, 1, 2)(4), w″_(2, 2, 2)(4)

Each rake finger 312 ₁-312 _(F) may communicate, as one or more signals318, its respective channel estimates, rake finger timing information,scrambling codes associated with one or more BTSs, and/or otherinformation to the interference cancellation module 302.

In various embodiments of the invention, the interference cancellationmodule 302 may receive chip-level signals 326 from the delay buffer 304.Based on the channel estimates, rake finger timing, and/or otherinformation communicated via the signal(s) 318, the interferencecancellation module 302 may select individual multipath signals from thechip-level signals 326 received via the delay buffer 304. Based on theinterference cancellation parameters 320, which may be as described withrespect to FIG. 2, the interference cancellation module 302 may processthe received chip-level multipath signal 326 utilizing an iterativemethod for interference cancellation, in accordance with an embodimentof the invention.

The chip-level signals 326 received from the delay buffer 304 maycomprise a plurality of multipath signals received via one or morereceive antennas from one or more transmit antennas of one or more BTSs.The interference cancellation module 302 may be configurable to assignsignal processing resources to perform the iterative method ofinterference cancellation for selected multipath signals. The processor206 may configure the interference cancellation module 302 to receivemultipath signals from one or more transmit antennas of one or moreBTSs. The processor 206 may configure the interference cancellationmodule 302 for receive diversity.

The interference cancellation module 302 may receive interferencecancellation parameters 320 from the processor 206 and/or from thememory 208. In an exemplary embodiment of the invention, theinterference cancellation module 302 may generate and/or retrieve PNsequences and/or OVSF codes from the memory 208. The interferencecancellation module 302 may retrieve and/or generate a PN sequence foreach of the one or more transmit antennas of the one or more BTSs fromwhich the interference cancellation module 302 is configured to attemptto receive a signal.

In various embodiments of the invention in which the receiver 202utilizes a plurality of receiving antennas and/or receives data from aplurality of transmit antennas, data received via the symbol-levelsignals corresponding to the plurality of receiving antennas and/ortransmit antennas may be decoded by utilizing various diversity decodingmethods. Various embodiments of the invention may also be practiced whenthe receiver 202 is utilized in a multiple input multiple output (MIMO)communication system. In instances where the receiver 202 is utilized ina MIMO communication system, data received via the symbol-level signals,received via the plurality of receiving antennas, may be decoded byutilizing various MIMO decoding and/or diversity decoding methods.

FIG. 4 is a module diagram illustrating an exemplary interferencecancellation module, in accordance with an embodiment of the invention.Referring to FIG. 4, there is shown an interference cancellation module302 comprising a channel estimate (CHEST) pre-processing module 401,interference cancellation per-cell modules 403A, 403B, 403C, 403D, ansubtractor 405, an HSDPA interpolation and delay module 407, a fingerMUX 409, and an interpolator 411.

The CHEST pre-processing module 401 may comprise suitable circuitry,logic, interfaces, and/or code that may be operable to normalize and/ororthogonalize channel estimate information input as signal 412 to thePer-Cell Modules 403 and the interpolator 411. The normalization may bebased on channel estimate and rake finger timing and scaling information318 received from the rake fingers 312 ₁-312 _(K). Additional details ofthe CHEST pre-processing module 401 are described below with respect toFIGS. 5-8.

The subtractor 405 may comprise suitable circuitry, logic, interfaces,and/or code that may be operable to subtract estimated signals fromreceived signals as part of the generation of an interference suppressedversion of the received signals. The subtractor 405 may be operable toreceive, as inputs, signals generated by the Per-Cell modules 403A-403Dthat may be interpolated by the interpolator 411, as well as 256-chipbursts of the delayed received signal 326 from the delay buffer 304.

The HSDPA interpolation and delay module 407 may comprise suitablecircuitry, logic, interfaces, and/or code that may be operable toprovide a bypass path for signals received from the delay buffer 304.The HSDPA interpolation and delay module 407 may, for example,interpolate cx2 samples to cx16 samples, and may introduce a delay thatequals the delay of the interference cancellation module 302 whenoperating in interference cancellation mode.

The finger MUX 409 may comprise suitable circuitry, logic, interfaces,and/or code that may be operable to select from the plurality of signals420 generated by the Per-Cell modules 403A-403D, the input signal fromthe delay buffer 304, or a non-cancelling finger input 424. In thismanner, the finger MUX 409 may enable a pass-through mode, aninterference cancelling mode, or a non-cancelling mode.

The interpolator 411 may comprise suitable circuitry, logic, interfaces,and/or code that may be operable to interpolate a received signal, suchas a cx1 signal and output a cx2 signal, for example.

The Per-Cell modules 403A-403D may each comprise suitable circuitry,logic, interfaces, and/or code that may be operable to generate anestimate of a multi-user (e.g., WCDMA) and/or multipath chip-levelsignal. Each of the Per-Cell modules 403A-403D may processbursts—256-chip bursts, for example—of a received multi-user and/ormultipath signal. A received signal 326 processed by each of the modules403A-403D may comprise information received on one or more RF channelsvia one or more receive antennas from one or more transmit antennas ofone or more BTSs, each BTS having up to J users. In this regard, each ofthe modules 403A-403D may be allocated for processing signals from aparticular transmit antenna of a particular BTS, where the signals froma particular transmit antenna may be received over one or more RFchannels via each of one or more receive antennas. Accordingly, each ofthe modules 403A-403D may be operable to provide compensation formultipath effects, suppress interference from BTSs other than anassociated or “serving” BTS, and suppress interference between users ofthe associated or “serving” BTS.

In an exemplary embodiment of the invention, the four Per-Cell modules403A-403D may be operable to cancel and/or suppress interference fromfour non-diversity transmit (Tx) BTSs, two Tx diversity BTSs, one Txdiversity BTS and two non-Tx diversity BTSs, one Tx diversity BTS withtwo scrambling codes per antenna, and/or one non Tx-diversity BTS thathas four scrambling codes. However, the invention need not be solimited, and may support any number of cells depending on the number ofPer-Cell modules integrated in the interference cancellation module.

In operation, each one of the per-cell modules 403 a-403 d may beallocated for processing signals from a particular transmit antenna ‘t’of a particular BTS ‘b’. Accordingly, each one of the per-cell modules403 a-403 d that processes signals from an antenna ‘t’ of a BTS ‘b’ mayreceive a set of normalized channel estimates w_(b,t,1)(1) . . .w_(b,t,R)(F(b)) from the CHEST pre-processing module 401. In thisregard, the CHEST pre-processing module 401 may generate the set ofnormalized channel estimates w_(b,t,1)(1) . . . w_(b,t,R)(F(b)) byprocessing the set of channel estimates w″_(b,t,1)(1) . . .w″_(b,t,R)(F(b)) received from the rake fingers 312 ₁-312 _(F(b)))allocated to processing signals from the antenna ‘t’ of BTS ‘b’.Processing of the set of channel estimates w″_(b,t,1)(1) . . .w″_(b,t,R)(F(b)) may comprise orthogonalization and/or normalization.

FIG. 5 is a diagram illustrating generation of normalized channelestimates, in accordance with an embodiment of the invention. Referringto FIG. 5 there is shown an exemplary CHEST pre-processing module 401comprising a switching element 502, an orthogonalization module 602, anda normalization module 702.

The switching module 502 may comprise suitable logic, circuitry,interfaces, and/or code that may be configurable such that channelestimates either bypass the orthogonalization module 602 or areprocessed by the orthogonalization module 602. The switching module 502may be controlled by one or more control signals from, for example, theprocessor 206 (FIG. 2).

The orthogonalization module 602 may comprise suitable logic, circuitry,interfaces, and/or code that may be operable to determine a measure ofcorrelation between a set of channel estimates from a first antenna of atransmit-diversity BTS and a set of channel estimates from a secondantenna of the transmit-diversity BTS. Based on the measure ofcorrelation, the orthogonalization module 602 may set each of thechannel estimates from the second antenna to zero. That is, signals fromthe second antenna may be disregarded or ignored for interferencecancellation processing. Alternatively, based on the measure ofcorrelation, the orthogonalization module 602 may rotate the set ofchannel estimates from the second transmit antenna such that the rotatedset of channel estimates is orthogonal to the set of channel estimatesfrom the first transmit antenna. In this regard, the set of channelestimates from the first transmit antenna may be represented as a firstvector having F(b) elements and the set of channel estimates from thesecond transmit antenna may be represented as a second vector havingF(b) elements. Accordingly, the second vector may be rotated such thatthe rotated vector is orthogonal to the first vector.

The normalization module 702 may comprise suitable logic, circuitry,interfaces, and/or code that may be operable to normalize channelestimates with respect to total power from a particular BTS or aparticular transmit antenna of a BTS received via one or more signalpaths. In this regard, in instances that signals are received from aparticular BTS or particular transmit antenna of a BTS via a singlepath, the channel estimates may be set to one. In instances that signalsfrom a particular BTS or particular transmit antenna are received over asingle path, then the channel estimates may be normalized to valuesbetween 0 and 1. In instances that signals from a particular BTS orparticular transmit antenna are received over multiple paths then thechannel estimates may be normalized to values between 0 and 1.

The normalization may ensure that the estimated interference signal tobe subtracted from a received signal is appropriately scaled. If theinterference signal is too large, the subtracted interference signal maybe more than the actual interference; this may have the undesired effectof effectively introduce interference. Conversely, if the interferencesignal is too small, the subtracted interference signal only representsa portion of the interference; this may have the undesired effect ofinterference remaining in the received signal after cancellation.

In operation, the switching module 502 may be dynamically configured aschannel estimates are received from the fingers 312 ₁-312 _(F). In thisregard, for estimates received from a finger 312 _(f) associated with anon-transmit-diversity BTS, the switching module 502 may route thechannel estimates w″_(b,t,r)(f) to the normalization module 702.Conversely, for estimates received from a finger 312 _(f) associatedwith a transmit-diversity BTS, the switching module 502 may route thechannel estimates w″_(b,t,r)(f) to the orthogonalization module 602.

In an exemplary embodiment of the invention, fingers 312 ₁-312 _(F(b))may be allocated for processing signals from a non-transmit-diversityBTS ‘b’. In such an embodiment, the set of channel estimatesw″_(b,1,1)(1) . . . w″_(b,1,R)(F(b)) may bypass the orthogonalizationmodule 602 and the set of normalized channel estimates w_(b,1,1)(1) . .. w_(b,1,R)(F(b)) may be generated by normalizing the set of channelestimates w″_(b,1,1)(1) . . . w″_(b,1,R)(F(b)) with respect to the totalsignal energy received via the rake fingers 312 ₁-312 _(F(b)). The setof normalized channel estimates w_(b,1,1)(1) . . . w″_(b,1,R)(F(b)) maybe communicated to the one of the per cell modules 403 a-403 d allocatedfor processing signals from the BTS ‘b’. The per-cell module may utilizethe normalized channel estimates for cancelling interference in signalsreceived from the BTS ‘b’. Channel estimates may be processed in thismanner for each non-transmit-diversity BTS for which there is a per-cellmodule 403 and one or more fingers 312 that are allocated.

In an exemplary embodiment of the invention, fingers 312 ₁-312 _(F(b))may be allocated for processing signals from a transmit-diversity BTS‘b’. In such an embodiment, the two sets of channel estimatesw″_(b,1,1)(1) . . . w″_(b,1,R)(F(b)) and w″_(b,2,1)(1) . . .w″_(b,2,R)(F(b)) may be routed to the orthogonalization module 602. Theorthogonalization module 602 may be operable to generate correspondingsets of channel estimates w′_(b,1,1)(1) . . . w′_(b,1,R)(F(b)) andw′_(b,2,1)(1) . . . w′_(b,2,R)(F(b)) which may be conveyed to thenormalization module 702, where each set of channel estimates may beprocessed in the same manner as a set of channel estimates from anon-transmit-diversity BTS.

The orthogonalization module 602 may be operable to determine a measureof correlation between the set of channel estimates w″_(b,1,1)(1) . . .w″_(b,1,R)(F(b)) and the set of channel estimates w″_(b,2,1)(1) . . .w″_(b,2,R)(F(b)). In instances that the measure of correlation is abovea threshold, the orthogonalization module 602 may generate a set ofchannel estimates w′_(b,2,1)(1) . . . w′_(b,2,R)(F(b)) in which allestimates are equal to zero. In this regard, the zeroed-out set channelestimates w″_(b,2,1)(1) . . . w″_(b,2,R)(F(b)) may not be utilized forinterference cancellation. Accordingly, the one of the per-cell modules403 a-403 d allocated for processing signals from antenna 2 of BTS ‘b’may be disabled and/or not utilized for interference cancellation. Ininstances that the measure of correlation is below a threshold, theorthogonalization module 602 may be operable to process the two sets ofchannel estimates w″_(b,1,1)(1) . . . w″_(b,1,R)(F(b)) and w″_(b,2,1)(1). . . w″_(b,2,R)(F(b)) to generate two sets of channel estimates,w′_(b,1,1)(1) . . . w′_(b,1,R)(F(b)) and w′_(b,2,1)(1) . . .w′_(b,2,R)(F(b)), that are orthogonal to each other.

The normalization module 702 may then normalize w′_(b,1,1)(1) . . .w′_(b,1,R)(F(b)) and w′_(b,2,1)(1) . . . w′_(b,2,R)(F(b)) to generatetwo sets of normalized channel estimates, w_(b,1,1)(1) . . .w_(b,1,R)(F(b)) and w_(b,2,1)(1) . . . w_(b,2,R)(F(b)). The set ofnormalized channel estimates w_(b,1,1)(1) . . . w_(b,1,R)(F(b)) may becommunicated to the one of the per cell modules 403 a-403 d allocatedfor processing signals from antenna 1 of the BTS ‘b’. The set ofnormalized channel estimates w_(b,2,1)(1) . . . w_(b,2,R)(F(b)) may becommunicated to the one of the per cell modules 403 a-403 d allocatedfor processing signals from antenna 2 of the BTS ‘b’.

Exemplary pseudocode illustrating operation of an exemplaryorthogonalization module 602 is as follows:

for b =1:B // loop BTSs for which there is at least one per-cell moduleallocated Delta=Cal1=Cal2=P1=P2=P3=0; // initialize variables ifblock_en==true // if the rotation block is enabled if F(b)==1 // bypassthe whole rotation part for cell b else for t=1:T(b) // loop through thetransmit antennas of the BTS b for r=1:R // loop through all the receiveantennas of the receiver for f=1:F(b) // loop through fingers allocatedto BTS b if t==1 // for the first transmit antenna w’_(b,1,r)(f) =w”_(b,1,r)(f) //bypass orthogonalization for ant. 1 else P1 = P1 +w”_(b,1,r) ^(H)(f) w”_(b,1,r)(f) // power of ant. 1 of BTS b P2 = P2 +w”_(b,2,r) ^(H)(f) w”_(b,2,r)(f) // power of ant. 2 of BTS b P3 = P3 +w”_(b,1,r) ^(H)(f) w”_(b,2,r)(f) // Inner product end // if t==1 end //for f=1:F(b) end // for r=1:R end // for f=1:T(b) if P1==0 // if thereis no signal energy received from the first antenna w’_(b,2,r)(f) =w”_(b,2,r)(f) // bypass orthogonalization for ant. 2 elseCal1=P1*P2*Rth; //Rth is the correlation thresholdCal2=P3.r*P3.r+P3.i*P3.i; //power of P3 if(Cal2>Cal1) // If measure ofcorrelation is above a threshold w’_(b,2,r)(f) = 0 for all b,r // zeroout estimates from antenna 2 else β = P3/P1 for r=1:R // loop over allreceive antennas for f=1:F(b) // loop through fingers allocated to theBTS b Delta = β*w”_(b,1,r)(f); w”_(b,2,r)(f) = w”_(b,2,r)(f); end // forf=1:F(b) end // for r=1:R end //if(Cal2>Cal1) end //if P1==0 end //F(b)==1 else // rotation block disabled w’_(b,t,r)(f)= w”_(b,t,r)(f) forall t, r, f // bypass everything for base station b end // ifblock_en==true end // for b =1:B

Exemplary pseudocode illustrating operation of an exemplarynormalization module 602 is as follows:

P(t) = 0 for all t; // initialize for b=1:B // loop BTSs for which thereis at least one per-cell module allocated if F(b)==1 // if there is onlyone path for BTS b for r=1:R // loop through all the receive antennas ofthe receiver w_(b,1,r)(1) = 1 w_(b,2,r)(1) = 0 end else for t=1:T(b) //loop through the transmit antennas of the BTS b for f=1:F(b) // loopthrough fingers allocated to BTS b for r=1:R // loop through all thereceive antennas of the receiver P(t) =sqrt(Re{w’_(b,t,r)(f)}{circumflex over ( )}2+lm{w’_(b,t,r)(f)}){circumflex over ( )}2+P(t){circumflex over ( )}2 )end end if (P(t)==0) w_(b,t,r)(f) = 0, for all f,r else w_(b,t,r)(f) =w’_(b,t,r)(f) / P(t) for all f,r end end end

FIG. 6A is a diagram that illustrates exemplary orthogonalization ofchannel estimates received from a transmit diversity antenna, inaccordance with an embodiment of the invention. Referring to FIG. 6Athere is shown two sets of input channel estimates w″_(b,1,1)(1) . . .w″_(b,1,R)(F(b)) and w″_(b,2,1)(1) . . . w″_(b,2,R)(F(b)), and two setsof output channel estimates w′_(b,1,1)(1) . . . w′_(b,1,R)(F(b) andw′_(b,2,1)(1) . . . w′_(b,2,R)(F(b)).

In operation, the input set of channel estimates corresponding to afirst transmit antenna may bypass the rotation module 604. That is, thechannel estimates w′_(b,1,1)(1) . . . w′_(b,1,R)(F(b)) may be the sameas the channel estimates w″_(b,1,1)(1) . . . w″_(b,1,R)(F(b)), butrenamed for convenience of illustration. On the other hand, the inputchannel estimates corresponding to a second transmit antenna areprocessed by the rotation module 604. That is, when the rotation moduleis enabled, the channel estimates w′_(b,2,1)(1) . . . w′_(b,2,R)(F(b))are a modified version of the channel estimates w″_(b,2,1)(1) . . .w″_(b,2,R)(F(b)).

In instances that the rotation module 604 is disabled, both sets ofinput channel estimates may pass directly to the output channelestimates. Conversely, in instances that the rotation module 604 isenabled, the output of the rotation module 604 may depend on a measureof correlation between the two sets of input channel estimates. In thisregard, in instances that the correlation between the two sets of inputchannel estimates are highly correlated (i.e. a measure of correlationbetween them is above a threshold), then the rotation module 604 mayoutput all zero values for the set w′_(b,2,1)(1) . . . w′_(b,2,R)(F(b)).That is, signals from the second antenna may be disregarded and/or notutilized for interference suppression. On the other hand, in instancesthat the two sets of input channel estimates are not highly correlated,then the set of input channel estimates w″_(b,2,1)(1) . . .w″_(b,2,R)(F(b)) may be processed to generate a set of channel estimatesw′_(b,2,1)(1) . . . w′_(b,2,R)(F(b)) that is orthogonal to the setw′_(b,1,1)(1) . . . w′_(b,1,R)(F(b).

Although FIG. 6A depicts modifying channel estimates corresponding to asecond antenna while channel estimates from a first antenna bypass suchmodification, the invention is not so limited. For example, channelestimates corresponding to a first antenna may be modified while channelestimates corresponding to a second antenna bypass the modification.Similarly, channel estimates corresponding to both antennas may bemodified. In this regard, how the channel estimates are modified is notimportant so long as the result is sets of channel estimates that areorthogonal to one another.

FIG. 6B and FIG. 6C are diagrams that illustrate exemplaryimplementation of an orthogonalization module, in accordance with anembodiment of the invention. In this regard, FIGS. 6B and 6C mayillustrate pictorially what is described above in the exemplarypseudocode for the orthogonalization module 602.

Referring to FIG. 6B, the multipliers 620 ₁-620 _(FB), the adder 626,and the formatting module 632 a may generate P1. Similarly, themultipliers 622 ₁-622 _(FB), the adder 628, and the formatting module632 b may generate P2. The multipliers 624 ₁-624 _(FB), the adder 630,and the formatting module 632 c may generate P3. The module 640 maygenerate Cal2 by determining the magnitude, or an approximation of themagnitude, of P3.

The decision block 634 may determine whether P1 is equal to zero. Ininstances that P1 is equal to zero, then the set of channel estimatesthe set of channel estimates w″_(b,2,r)(f) may pass through to becomew′_(b,2,r)(f). That is, orthogonalization may be bypassed.

In instances that P1 is not equal to zero, multiplier 636 may multiplyP1 and P2, multiplier 638 may multiple the output of multiplier 636 by acorrelation threshold to generate Cal1. The correlation threshold may beprogrammed via, for example, firmware. The comparison block 642 maydetermine whether Cal2 is greater than Cal1. In instances that Cal 2 isgreater, then w′_(b,2,r)(f) may be set to zero for all r and fassociated with the BTS ‘b’. In instances that Cal2 is not greater,then, referring now to FIG. 6C, P3 may be divided by P1 in block 652.The output of block 652 may be multiplied by w′_(b,1,r)(f), for all rand f associated with the BTS ‘b’, via the multiplier 656. The output ofmultiplier 565 may be multiplied by a formatted version ofw′_(b,2,r)(f), for all r and F associated with BTS ‘b’, via themultiplier 658. The output of the multipler 658 may be the modified setof channel estimates w′_(b,2,r)(f).

Also shown in FIGS. 6B and 6 c are various formatting modules 632. Theformatting module 632 may, for example, adjust a bit-width, left-shift,right-shift, or adjust a sample rate of a signal. One or more of theformatting modules 632 may be optional.

It should be noted that FIG. 6B is a functional block diagram that doesnot necessarily depict a hardware configuration of the orthogonalizationmodule 602. In this regard, various operations associated withorthogonalization may be performed sequentially by shared hardwareand/or in parallel by separate hardware modules or blocks and theinvention is not limited to any particular hardware implementation.

FIG. 7 is a diagram that illustrates an exemplary implementation of anormalization module, in accordance with an embodiment of the invention.In this regard, FIG. 7 may illustrate pictorially what is describedabove in the exemplary pseudocode for the normalization module 702.Referring to FIG. 7, the modules 752 and 753 may generatepseudo-amplitude values to generate P(i). The decision block 754 maydetermine whether P(i) is equal to 0, for all i. In instances that P(i)is equal to 0 for all i, then the set of channel estimates w_(b,t,r)(f)may be set to 0 for all r and f associated with BTS ‘b’. In instancesthat P(i) is not equal to 0 for all i, then ‘a’—generated byleft-shifting w′_(b,t,r)(f)—may be divided by P(i) in block 756. Ifthere is more than one finger associated with the BTS then the output ofthe block 756 may be selected as the set of channel estimatesw_(b,t,r)(f) for all t, r, and f associated with BTS ‘b’. In instancesthat there is only one finger associated with BTS ‘b,’ then w_(b,t,r)(f)may be set to 1 for all t, r, and f associated with BTS ‘b’.

FIG. 8 is a flowchart illustrating exemplary steps for interferencecancellation in a communication system that utilizes transmit diversity,in accordance with an embodiment of the invention. Referring to FIG. 8,the exemplary steps may begin with step 802 when the rake fingers 312₁-314 _(F) may be allocated among one or more BTSs. That is, each fingermay be associated with a particular BTS. In step 804, wireless signalsmay be received by the receiver 300 from the one or more BTSs. In step806, each finger may begin generating channel estimates that estimatethe complex channel gain from the one or more transmit antennas of theassociated BTS to a particular receive antenna of the receiver 300. Instep 808, for each finger, it may be determined whether the associatedBTS utilizes transmit diversity. For fingers that are associated with atransmit diversity BTS, the exemplary steps may advance to step 812.

In step 812, for each finger associated with a transmit-diversity BTS,it may be determined whether a measure of correlation between a set ofchannel estimates for a first transmit antenna of the associated BTS anda set of channel estimates for a second transmit antenna of theassociated BTS is above a threshold. In instances that the measure ofcorrelation is above a threshold, the exemplary steps may advance tostep 814. In step 814, for each finger associated with atransmit-diversity BTS, the second set of channel estimates generated bythe finger may be processed such that the result is orthogonal to thefirst set of channel estimates generated by the finger.

In step 810, for each finger, the channel estimates corresponding to thefinger may be normalized. For channel estimates corresponding to afinger f, the normalization may be done with respect to the total energyreceived by all fingers associated with the same BTS.

In step 818, each set of normalized estimate may be conveyed to acorresponding per-cell module. In step 820, the per-cell modules mayperform interference cancellation utilizing the normalized channelestimates.

Returning to step 812, in instances that the measure of correlation isabove a threshold, the exemplary steps may advance to step 816 in whichthe channel estimates to be output to the corresponding per cell modulemay be set to zero. In this regard, a per-cell module that receives thezeroed out channel estimates may not cancel interference. In thismanner, aspects of the invention may prevent double cancellation of thesame interference.

Returning to step 808, for channel estimates from fingers associatedwith a non-transmit-diversity BTS, the exemplary steps may advance tothe step 810.

Aspects of a method and system for channel estimation for interferencesuppression are provided. In an exemplary embodiment of the invention,one or more circuits and/or processors of the CHEST pre-processingmodule 401 may generate and/or receive a first set of channel estimatesw″_(b,1,r)(1) . . . w″_(b,1,r)(F(b)) and a second set of channelestimates w″_(b,2,r)(1) . . . w″_(b,2,r)(F(b)). The first set of channelestimates may be associated with a plurality of RF channels between afirst transmit antenna 152A of a base transceiver station 102 and one ormore receive antennas 222 of the mobile communication device 114. Thesecond set of channel estimates may be associated with a plurality of RFchannels between a second transmit antenna 152D of the base transceiverstation 102 and one or more receive antennas 222 of the mobilecommunication device 114. The one or more circuits and/or processors maymodify the second set of channel estimates based on a comparison of ameasure of correlation between the first set of channel estimates andthe second set of channel estimates with a threshold. The first set ofchannel estimates w″_(b,1,r)(1) . . . w″_(b,1,r)(F(b)) and/or themodified second set of channel estimates w′_(b,2,r)(1) . . .w′_(b,2,r)(F(b)) may be utilized for processing received signals. Ininstances that the measure of correlation is below the threshold, thesecond set of channel estimates may be modified such that the modifiedsecond set of channel estimates w′_(b,2,r)(1) . . . w′_(b,2,r)(F(b)) isorthogonal to the first set of channel estimates w″_(b,1,r)(1) . . .w″_(b,1,r)(F(b)). In instances that the measure of correlation is abovethe threshold, the second set of channel estimates may be modified suchthat the modified second set of channel estimates w′_(b,2,r)(1) . . .w′_(b,2,r)(F(b)) is a set of zeros.

The first set of channel estimates may be normalized with respect tototal power received over all of the plurality of RF channels betweenthe first transmit antenna 152A and the one or more receive antennas222. The second set of channel estimates may be normalized with respectto total power received over all of the plurality of RF channels betweenthe second transmit antenna 152D and the one or more receive antennas.The threshold may be dynamically determined. The second set of channelestimates may be disregarded in instances that the measure ofcorrelation is above a threshold. Each channel estimate in the first setof channel estimates may indicate a complex channel gain between thefirst transmit antenna 152A and one of the one or more receive antennas222. Each channel estimate in the second set of channel estimates mayindicates a complex channel gain between the second transmit antenna152D and one of the one or more receive antennas 222. The basetransceiver station 102 may be a non-listened base transceiver station.Interference may be suppressed in the received signals based on thefirst set of channel estimates and/or the modified second set of channelestimates.

Another embodiment of the invention may provide a machine and/orcomputer readable medium, having stored thereon, a computer programhaving at least one code section executable by a machine and/orcomputer, thereby causing the machine and/or computer to perform thesteps as described herein for channel estimation for interferencesuppression.

Accordingly, the present invention may be realized in hardware,software, or a combination of hardware and software. The presentinvention may be realized in a centralized fashion in at least onecomputer system, or in a distributed fashion where different elementsare spread across several interconnected computer systems. Any kind ofcomputer system or other apparatus adapted for carrying out the methodsdescribed herein is suited. A typical combination of hardware andsoftware may be a general-purpose computer system with a computerprogram that, when being loaded and executed, controls the computersystem such that it carries out the methods described herein.

The present invention may also be embedded in a computer programproduct, which comprises all the features enabling the implementation ofthe methods described herein, and which when loaded in a computer systemis able to carry out these methods. Computer program in the presentcontext means any expression, in any language, code or notation, of aset of instructions intended to cause a system having an informationprocessing capability to perform a particular function either directlyor after either or both of the following: a) conversion to anotherlanguage, code or notation; b) reproduction in a different materialform.

While the present invention has been described with reference to certainembodiments, it will be understood by those skilled in the art thatvarious changes may be made and equivalents may be substituted withoutdeparting from the scope of the present invention. In addition, manymodifications may be made to adapt a particular situation or material tothe teachings of the present invention without departing from its scope.Therefore, it is intended that the present invention not be limited tothe particular embodiment disclosed, but that the present invention willinclude all embodiments falling within the scope of the appended claims.

1. A method for signal processing, the method comprising: performing byone or more circuits and/or processors in a mobile communication device:comparing with a threshold, a value that corresponds to a measure ofcorrelation between a first set of channel estimates and a second set ofchannel estimates; cancelling interference in received signals utilizingsaid first set of channel estimates, when said value is above saidthreshold; and modifying said second set of channel estimates andcancelling interference in received signals utilizing said first set ofchannel estimates and said modified second set of estimates, when saidvalue is below said threshold.
 2. The method according to claim 1,wherein: said first set of channel estimates are associated with aplurality of RF channels between a first transmit antenna of a basetransceiver station and one or more receive antennas of said mobilecommunication device; and said second set of channel estimates areassociated with a plurality of RF channels between a second transmitantenna of a base transceiver station and one or more receive antennasof said mobile communication device.
 3. The method according to claim 1,comprising modifying one or both of said first set of channel estimatesand said second said of channel estimates to generate two sets ofchannel estimates that are orthogonal, when said value is below saidthreshold.
 4. The method according to claim 1, comprising modifying saidsecond set of channel estimates by setting each estimate in the secondset to zero, when said value is above said threshold.
 5. The methodaccording to claim 1, comprising normalizing said first set of channelestimates with respect to total power received over said plurality of RFchannels between said first transmit antenna and said one or morereceive antennas.
 6. The method according to claim 1, comprisingnormalizing said second set of channel estimates with respect to totalpower received over said plurality of RF channels between said secondtransmit antenna and said one or more receive antennas.
 7. The methodaccording to claim 1, comprising dynamically determining said threshold.8. The method according claim 1, comprising disregarding said second setof channel estimates when said value is above said threshold.
 9. Themethod according to claim 1, wherein each channel estimate in said firstset of channel estimates indicates a complex channel gain between saidfirst transmit antenna and one of said one or more receive antennas. 10.The method according to claim 1, wherein each channel estimate in saidsecond set of channel estimates indicates a complex channel gain betweensaid second transmit antenna and one of said one or more receiveantennas.
 11. The method according to claim 1, wherein said basetransceiver station is a non-listened base transceiver station.
 12. Themethod according to claim 1, comprising suppressing interference in saidreceived signals based on said first set of channel estimates and/orsaid modified second set of channel estimates.
 13. A system for signalprocessing, the system comprising: one or more circuits and/orprocessors for use in a mobile communication device, wherein said one ormore circuits are operable to: compare with a threshold a value thatcorresponds to a measure of correlation between a first set of channelestimates and a second set of channel estimates; cancelling interferencein received signals utilizing said first set of channel estimates, whensaid value is above said threshold; and modify said second set ofchannel estimates and cancelling interference in received signalsutilizing said first set of channel estimates and said modified secondset of estimates, when said value is below said threshold.
 14. Thesystem according to claim 13, wherein: said first set of channelestimates are associated with a plurality of RF channels between a firsttransmit antenna of a base transceiver station and one or more receiveantennas of said mobile communication device; and said second set ofchannel estimates are associated with a plurality of RF channels betweena second transmit antenna of a base transceiver station and one or morereceive antennas of said mobile communication device.
 15. The systemaccording to claim 13, wherein said one or more circuits and/orprocessors are configured to modify one or both of said first set ofchannel estimates and said second said of channel estimates to generatetwo sets of channel estimates that are orthogonal, when said value isbelow said threshold.
 16. The system according to claim 13, wherein saidone or more circuits and/or processors are configured to modify saidsecond set of channel estimates by setting each estimate in the secondset to zero, when said value is above said threshold.
 17. The systemaccording to claim 13, wherein said one or more circuits and/orprocessors are configured to normalize said first set of channelestimates with respect to total power received over said plurality of RFchannels between said first transmit antenna and said one or morereceive antennas.
 18. The system according to claim 13, wherein said oneor more circuits and/or processors are configured to normalize saidsecond set of channel estimates with respect to total power receivedover said plurality of RF channels between said second transmit antennaand said one or more receive antennas.
 19. The system according to claim13, wherein said one or more circuits and/or processors are configuredto dynamically determine said threshold.
 20. The system according claim13, wherein said one or more circuits and/or processors are configuredto disregard said second set of channel estimates, when said value isabove said threshold.
 21. The system according to claim 13, wherein eachchannel estimate in said first set of channel estimates indicates acomplex channel gain between said first transmit antenna and one of saidone or more receive antennas.
 22. The system according to claim 13,wherein each channel estimate in said second set of channel estimatesindicates a complex channel gain between said second transmit antennaand one of said one or more receive antennas.
 23. The system accordingto claim 13, wherein said base transceiver station is a non-listenedbase transceiver station.
 24. The system according to claim 13, whereinsaid one or more circuits and/or processors are configured to suppressinterference in said received signals based on said first set of channelestimates and/or said modified second set of channel estimates.